Copyright © 2010, 2011 by Wayne Stegall
Updated March 26, 2011. See Document History at end for
details.
Low-noise
Hybrid
Op-amp/Discrete
Phono
Preamp
Introduction
Desiring to present a RIAA
equalization design example using an operational amplifier, it seems
natural to prefer the part with the lowest known noise
specification. Analog Devices AD797 is probably the first device
to mind with this qualification. This part, however, has a
dominant
pole of about 7.4Hz. However, its enormous gain and wide
bandwidth reduce
distortion to levels well below those thought to be audible regardless
of the preceding pole specification. That some say it has a
excellent but dark sound is additional confirmation of complete lack of
audible distortion. Because I wanted to have a switchable extra
50kHz zero, I chose the required output buffer following this function
to be discrete. The current-source-biased source-follower buffer
is a very low distortion circuit, which I want to add a neutral
euphonic distortion profile. The capacitor is not a detriment in
this circuit because it would likely have been needed even with an
op-amp output buffer. This is because the 60dB DC gain and
class-a pull up resistor of the first stage would have produced a good
bit
more offset than a low gain op-amp application. A capacitor or a
dc servo would have been desired regardless. This circuit also
benefits because
an operational amplifier RIAA circuit simplifies setting gain and
equalization compared to a discrete circuit with its transistor
variations and stray impedances.
The schematic and SPICE analyses were created with a limited version of
National Instrument's MultiSim offered by Analog Devices to evaluate
their products. As such, all parts available in the program were
either Analog Devices components or enough generic parts needed to
complete a design. I maxed the parts count in the schematic
below. Therefore, I could not show paralled standard value
capacitors separately.
Theory of operation
Operational amplifier U1
and its
feedback circuit amplify and equalize the input signal to RIAA
specifications adding an extra 50kHz zero. R4 and C4
create a 50kHz pole which switch S1 will use to allow or
cancel the
extra
50kHz zero. The output buffer serves to isolate the RC filter and
drive the load. Furthur, the output buffer puts the very high
impedance of its JFET's drains
between each power supply connection and the signal path. I
intend this to
create PSRR (power supply rejection ratio) high enough to reduce power
supply concerns in this stage.
Circuit
Figure
1:
Schematic
showing
ideal
equalization
values.
Chosen
standard
values
follow
in
parts
list.
|
|
Parts List
|
|
|
|
U11
|
Analog Devices AD797AN
|
C2a4 |
100nF, 1% |
Q1, Q22
|
2N5434 n-ch JFET
|
C2b4 |
2.2nF, 1% |
Ri3
|
47kΩ, 5%
|
RBIAS
|
3kΩ, 5%
|
Ci3
|
100pF, 5% |
R4
|
1.0kΩ, 1%
|
R1 |
9.09kΩ, 1% |
C4a4 |
3nF, 1% |
R2 |
732Ω, 1% |
C4b4 |
180pF, 1%
|
R3a |
31.6Ω, 1% |
S1
|
½ of DPDT switch or relay
(shared with other channel)
|
R3b |
10.0Ω, 1% |
RS |
75Ω, 5%
|
C1a4 |
330nF, 1% |
C3 |
270µF, 10% electrolytic
|
C1b4 |
20nF, 1% |
RL5 |
100kΩ, 5% |
1A new National
Semiconductor operational amplifier LME49990 has specifications nearly
identical to Analog Devices
AD797, if you desire to investigate an alternative to this part.
It is less hobby friendly because, unlike the AD797, it only available
as a surface mount component.
2This part chosen from limited parts list. I
expect you will make substitutions for this part. See design
procedure.
3Ri and Ci, are not shown in the
circuit, connect them from input to ground. Values calculated for
your
cartidge can be substituted for default values shown.
4A and b subdesignations of parts indicate parallel
combinations meant to serve one part function.
5RL in circuit is altered to test
distortion under lowest normal load condition. The actual value
is used to properly terminate C3.
|
Design Procedure
Calculate RIAA Analysis
See
Calculating
Non-inverting RIAA
Network with Extra Zero for details and derivation of these
calculations.
Choose R
3b = 10Ω from AD797 datasheet
recommendation.
(1)
|
R3 =
|
R3b
0.2382778 |
=
|
10Ω
0.2382778 |
= 41.9678Ω |
(2)
|
R3a = R3 -
R3b = 41.9678Ω - 10Ω
= 31.9678Ω |
(3) |
R2 = R3
× 17.67514356 = 41.9678Ω × 17.67514356 = 741.787Ω |
(4)
|
R1 = R3
× 217.173913 = 41.9678Ω × 217.173913 = 9.11431kΩ |
(5)
|
C1 =
|
TP1
R1
|
=
|
3180µs
9.11431kΩ |
= 348.902nF
|
(6)
|
C2 =
|
TP2
R2
|
=
|
75µs
741.787Ω |
= 101.107nF
|
Now calculate extra-zero switch out circuit:
Choose R
4 = 1kΩ and calculate for C
4:
(7)
|
C4 = |
TZ2
R4 |
=
|
3.18µs
1kΩ |
= 3.18nF
|
Calculate Class-A Biasing
Here the concept is that applying the supply voltage through a voltage
divider comprising R
BIAS and the lowest load resistance
expected should result in a voltage across the load exceeding the
maximum expected peak signal. Assuming a minimum load of 10kΩ and
a peak signal of 2.828V calculate:
(8)
|
RBIAS-MAX = 10kΩ × |
15V - 2.828V
15V
|
= 8.11467kΩ |
For the purpose of allowing headroom calculate R
BIAS for a
reasonable bias within the selected op amp's current capacity.
Choose 5mA bias and calculate R
BIAS:
(9)
|
RBIAS-MIN = |
15V
5mA
|
= 3kΩ |
Choose lower of two R
BIAS calculations:
Connect this bias to positive supply to have any dc offset contribution
pull output capacitor in the same direction as the output buffer
does. This is to prevent capacitor bias uncertainty in the
unlikely event that the class-a bias produces an offset near to the
operating value of V
GS.
Output Buffer Design
The limits of the trial edition of MultiSim limited my choice of
JFET's. It is fortunate then that this choice is not
critical. As for noise the op-amp has amplified its noise enough
to make that of the output less critical. Consider that 1nV/√Hz
amplified by about 100 gain at 1kHz is 100nV/√Hz. A common
2N3819 would be a good choice as would others in this respect. It
is better to prioritize the maximization of g
fs in order to
reduce buffer stage distortion. To this end, an LSK170 would be a
best known choice due to high k
n and g
fs, with
the lowest possible noise for a bonus. The best compromise choice
given me by MultiSim was a 2N5434 with a k
n of 22mA/V
2.
Even
this
part
is
now
obsolete.
Since
you
would
be
faced
with
component
variations
on
a
part
of
your
own
choice,
I
suggest
you
choose
a
value
of
R
S by trial and error to get a bias current
within your JFETs specifications. You should not match Q
1
and Q
2. Rather, because Q
1 will operate
freer if
it is not pushed to its current limit, you should choose Q
1
to have a higher g
fs than Q
2. To this end,
try both transistors in the Q
2 position and place the one
there that gives the lowest bias current through Q
2.
Since this aspect is experimental, calculating R
S may be
overengineering. A R
S corresponding to the JFET's
rated g
fs would be a good starting point for a midpoint
bias, i.e.:
(11)
|
RS =
|
1
gfs |
=
|
1
17mS |
= 58.8235Ω |
or alternatively setting R
S to ratio of cutoff voltage to
maximum current for another approximate midpoint bias:
(12)
|
RS =
|
|VT|
|IDSS| |
=
|
2.5V
30mA |
= 83.3333Ω |
If you must make an exact calculation from a chosen I
D, the
following was derived from the FET equation by circuit analysis:
(13)
|
RS =
|
VT
- sqrt(ID/kn)
ID |
Choose R
S =
75Ω as
median of two estimates.
Calculate output coupling capacitor to give 1Hz highpass pole with a
600Ω load knowing that the pole frequency will be much lower with a
more reasonable load of 10kΩ:
(14)
|
C3 =
|
1
2π × RL-MIN × fhp |
=
|
1
2π × 600Ω × 1Hz |
= 265.2582385µF |
Round up to next standard value C
3 =
270µF
Spice Simulation
SPICE
model for
ideal circuit.
SPICE
model for
final circuit.
Magnitude in all Bode plots and Voltage in distortion plots are in
units of dB.
Figure
2:
Bode
and
phase
plots
from
ideal
circuit
before
choosing
standard
values.
Cyan plot shows 50kHz zero
switched in and magenta plot out.
|
|
Figure 3:
Same plots with circuit driven by RIAA inverse preequalizer
with extra pole at 50kHz.
Cyan plot shows 50kHz
zero switched in and magenta plot out.
|
|
Juggle ac analysis in SPICE to choose standard values:
Figure
4:
Preequalized
bode
plot
with
chosen
standard
values.
Cyan plot shows 50kHz zero
switched in and magenta plot out.
|
|
All Distortion analyses done with RIAA preequalization to give signal
levels the correct frequency balance.
Figure 5: Fourier analysis shows harmonic distribution of
0.0022818%
distortion of 1kHz signal. Note dominance of second harmonic and
to a lesser extent the other even harmonics.
|
|
Figure 6: 2rd harmonic distortion plot
magenta plot shows
op-amp
distortion rising with frequency and cyan plot shows it masked by
frequency-flat distortion profile of output stage.
|
|
Figure 7: 3rd harmonic distortion plot
magenta plot shows
op-amp
distortion rising with frequency and cyan plot shows it masked by
frequency-flat distortion profile of output stage. |
|
Miscellaneous Spice Results
|
SNR = 99.7334dB relative to 1VRMS
output.
AC analyses with ac sources in series with power supplies showed high
PSRR in output buffer: PSRR measured 91dB relative to VCC
and higher
relative to VEE. I did this investigation at the
outset to verify my presumptions about the buffer's PSRR and do not
remember the second figure exactly. This suggests that a power
supply sufficient for the first stage will suffice for the buffer as
well.
|
Final Comments
Although expected, I was gratified that the distortion results were
entirely those of the output buffer, showing little effect by the
operational amplifier.
Document History
October 29, 2010 Created.
October 29, 2010 Improved visibility of graphs.
October 30, 2010 Added links to semiconductor datasheets in parts
list.
October 30, 2010 Move class-a bias to connect to positive supply,
and verify no operational changes.
October 31, 2010 Added specific reference to LME79990 as an
alternative op-amp and a link to its datasheet.
January 26, 2011 Made minor symbol improvements.
March 26, 2011 Made minor improvements to text.